Nested transimpedance amplifier

ABSTRACT

A nested transimpedance amplifier (TIA) circuit comprises a zero-order TIA having an input and an output. A first operational amplifier (opamp) has an output and an input that communicates with said output of said zero-order TIA. A first power supply input applies a first voltage to the zero-order TIA. A second power supply input receives a second voltage. A charge pump module develops a third voltage based on the first voltage and the second voltage, wherein the third voltage is applied to the opamp.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a divisional of U.S. patent application Ser. No.11/495,813, filed Jul. 28, 2006, which claims the benefit of U.S.Provisional Application No. 60/817,268, filed Jun. 29, 2006, 60/798,480,filed May 8, 2006, 60/798,567, filed May 8, 2006, and 60/759,899, filedJan. 18, 2006, and is a continuation-in-part of U.S. patent applicationSer. No. 10/459,731 filed Jun. 11, 2003, which is a continuation-in-partof U.S. Pat. No. 6,762,644 issued on Jul. 13, 2004, which claims thebenefit of U.S. Provisional Application No. 60/275,109, filed Mar. 13,2001. The aforementioned applications are hereby incorporated byreference in their entirety.

FIELD OF THE INVENTION

The present invention relates to transimpedance amplifiers, and moreparticularly to nested transimpedance amplifiers with an increasedgain-bandwidth product.

BACKGROUND OF THE INVENTION

A transimpedance amplifier (TIA) is a well-known type of electroniccircuit. Referring now to FIG. 1, a TIA 100 includes an operationalamplifier (opamp) 105 having a gain parameter (−g_(m)). The opamp 105 isconnected in parallel to a resistor (R_(f)) 110. The input to the TIA100 is a current (Δi) 115. The output of the TIA 100 is a voltage(Δv_(o)) 120.

Referring now to FIG. 2, the opamp 105 of the TIA 100 is replaced by acurrent source 205 and a transistor 210 having gain −g_(m). The TIA 100in FIGS. 1 and 2 is often referred to as a transconductance amplifierbecause it converts the input current Δi into the output voltage Δv_(o).

Referring now to FIG. 3, a TIA 300 converts an input voltage (Δv_(i))305 into an output voltage (Δv_(o)) 310. The TIA 300 also includes aresistor 315 that is connected to a transistor 320. The TIA 300 istypically used in applications that require relatively low bandwidth.

Referring now to FIG. 4, a TIA 400 converts an input voltage (Δv_(i))405 into an output voltage (Δv_(o)) 410. The TIA 400 includes a secondopamp 415, which is connected in series to a parallel combination of aresistor (R_(f)) 420 and an opamp 425. The TIA 400 is typically used forapplications having higher bandwidth requirements than the TIA 300.

Ordinarily, the bandwidth of the TIA is limited to a fraction of athreshold frequency f_(T) of transistor(s) that are used in theopamp(s). In the case of a bipolar junction transistor (BJT) such as agallium-arsenide (GaAs) transistor, the bandwidth of the TIA isapproximately equal to 10%-20% of f_(T). For metal-oxide-semiconductor(MOS) transistor(s), the bandwidth of the TIA is typically a few percent(i.e., approximately 2%-6%) of f_(T).

Referring now to FIG. 5, a TIA 500 may be configured to operatedifferentially using two inputs of each opamp 502 and 504. One input 505acts as a reference, in a similar manner as ground or virtual ground ina standard configuration TIA. The input voltage Δv_(i) and the outputvoltage Δv_(o) are measured as voltage differences between a referenceinput 505 and a second input 510. Feedback resistors 514 and 516 areconnected across the inputs and the outputs of the opamp 504.

Referring now to FIG. 6, one TIA application having a relatively highbandwidth requirement is that of an optical sensor. An optical sensorcircuit 600 includes the opamp 105 and the resistor 110 of the TIA 100that are coupled with a photodiode 605. The output of the photodiode 605is a current I_(photo) 610, which acts as an input to the TIA 100.

Increasingly, applications require both high bandwidth and high gain.Examples include optical sensors, such as fiber optic receivers, andpreamplifier writers for high-speed hard disk drives.

SUMMARY OF THE INVENTION

A nested transimpedance amplifier (TIA) circuit includes a zero-orderTIA having an input and an output, and a first operational amplifier(opamp). The opamp includes an input that communicates with said outputof said zero-order TIA, a first transistor driven by said input, asecond transistor that is driven by a first bias voltage andcommunicates with said first transistor, a first current source thatcommunicates with said second transistor, and an output at a nodebetween the first transistor and the second transistor.

In other features a second current source communicates with the firsttransistor. A gain of the opamp is greater than a gain of the zero-orderTIA. A bandwidth of the opamp is less than a bandwidth of the zero-orderTIA.

In other features the zero-order TIA includes a first opamp including afirst input and a first output, a second opamp including a second inputand a second output. The second input communicates with the firstoutput. A resistance includes one end that communicates with the secondoutput and a second end that communicates with the second input.

A nested differential mode transimpedance amplifier (TIA) circuitincludes a zero-order differential mode TIA including first and secondinputs and first and second outputs and a first differential modeoperational amplifier (opamp). The opamp includes inputs thatcommunicate with respective ones of said outputs of said zero-orderdifferential mode TIA, a first transistor driven by a first said input,a second transistor driven by a second said input, a third transistorthat is driven by a first bias voltage and communicates with said firsttransistor, a fourth transistor that is driven by the first bias voltageand communicates with said second transistor, a first current sourcethat communicates with said third transistor, a second current sourcethat communicates with said fourth transistor, and first and secondoutputs at respective connections between the first transistor and thethird transistor, and between the second transistor and the fourthtransistor.

In other features the nested differential mode TIA circuit includes athird current source that communicates with the first transistor and thesecond transistor. A gain of the first differential mode opamp isgreater than a gain of the zero-order differential mode TIA. A bandwidthof the first differential mode opamp is less than a bandwidth of thezero-order differential mode TIA.

In other features the zero-order differential mode TIA includes a seconddifferential mode opamp including inputs and outputs and a thirddifferential mode opamp including inputs and outputs. The inputs of thethird differential mode opamp communicate with respective outputs of thesecond differential mode opamp. Resistances include first ends andsecond ends. The first and second ends communicate with respectiveinputs and outputs of the third differential mode opamp.

A nested differential mode transimpedance amplifier (TIA) circuitincludes a zero-order differential mode TIA having first and secondinputs and first and second outputs, and a differential-mode push-pullopamp having first and second inputs and first and second outputs. Thefirst and second inputs communicate with respective ones of said firstand second outputs of said zero-order differential mode TIA.

In other features a gain of the differential-mode push-pull opamp isgreater than a gain of the zero-order differential mode TIA and abandwidth of the differential-mode push-pull opamp is less than abandwidth of the zero-order differential mode TIA.

In other features the zero-order differential mode TIA includes a seconddifferential mode opamp including inputs and outputs and a thirddifferential mode opamp including inputs and outputs. The inputs of thethird differential mode opamp communicate with respective outputs of thesecond differential mode opamp. Resistances include first ends andsecond ends. The first and second ends communicate with respectiveinputs and outputs of the third differential mode opamp.

A nested transimpedance amplifier (TIA) circuit includes a zero-orderTIA having an input and an output, a first operational amplifier (opamp)having an output and an input that communicates with said output of saidzero-order TIA, a first power supply input for applying a first voltageto the zero-order TIA, and a second power supply input for receiving asecond voltage. A charge pump module develops a third voltage based onthe first voltage and the second voltage. The third voltage is appliedto the opamp.

In other features the zero-order TIA includes a first opamp including afirst input and a first output and a second opamp including a secondinput and a second output. The second input communicates with the firstoutput. A resistance includes one end that communicates with the secondoutput and a second end that communicates with the second input.

In other features a voltage regulator regulates the second voltage. Alight-emitting diode communicates with the opamp output. The firstvoltage is greater than the second voltage. The third voltage isapproximately equal to a sum of the first voltage and the secondvoltage. The first voltage is otherwise applied to analog circuitry andthe second voltage is otherwise applied to digital circuitry. The firstvoltage is between about 2.5V and 3.3V. The second voltage is about1.2V.

A differential transimpedance amplifier circuit comprises a firstoperational amplifier having a first inverting input, a firstnon-inverting input, a first inverting output and a first non-invertingoutput; a second operational amplifier having a second inverting input,a second non-inverting input, a second inverting output and a secondnon-inverting output, wherein the second inverting output communicateswith the first non-inverting input and the second non-inverting outputcommunicates with the first inverting input; a first feedback elementthat communicates with the first non-inverting input and the firstinverting output; a second feedback element that communicates with thefirst inverting input and the first non-inverting output; a thirdfeedback element that communicates with the second inverting input andthe first inverting output; and a fourth feedback element thatcommunicates with the first non-inverting input and the firstnon-inverting output.

In other features, the third and fourth feedback elements comprise firstand second resistances, respectively. The third and fourth feedbackelements comprise first and second capacitances, respectively. The firstand second feedback elements comprise first and second resistances,respectively. The first and second feedback elements comprise first andsecond capacitances, respectively. The first and second feedbackelements each comprise a first resistance in series with an inductanceand a second resistance that are in parallel with a capacitance. Thecapacitance includes a variable capacitance. The first and secondfeedback elements each comprise a resistance in parallel with acapacitance. The capacitance includes a variable capacitance.

In other features, the first and second feedback elements each comprisea first resistance in series with an inductance and that are in parallelwith a capacitance and a second resistance. The capacitance includes avariable capacitance. The first and second operational amplifiers aretransconductance amplifiers.

In other features, an integrator comprises the differentialtransimpedance amplifier.

A single-nested transimpedance amplifier circuit comprises a thirdoperational amplifier having a third inverting input, a thirdnon-inverting input, a third inverting output and a third non-invertingoutput; and the differential transimpedance amplifier circuit. Thesecond inverting input communicates with the third non-inverting outputand the second non-inverting input communicates with the third invertingoutput.

A double-nested differential transimpedance amplifier circuit comprisesa single-nested transimpedance amplifier circuit; and a fourthoperational amplifier having a fourth inverting input, a fourthnon-inverting input, a fourth inverting output and a fourthnon-inverting output. The fourth inverting output communicates with thethird non-inverting output and the fourth non-inverting outputcommunicates with the third inverting input.

In other features, a fifth feedback element communicates with the fourthinverting output and the first inverting output. A sixth feedbackelement communicates with the fourth non-inverting output and the firstnon-inverting output. The fifth and sixth feedback elements comprisefirst and second resistances, respectively. The fifth and sixth feedbackelements comprise first and second capacitances.

A Sigma-Delta analog to digital converter comprises the differentialtransimpedance amplifier. The Sigma-Delta analog to digital convertercomprises a difference amplifier module that includes one input thatreceives an input signal; an integrator module that communicates with anoutput of the difference amplifier module; a comparator module thatreceives an output of the integrator module; and a digital to analogconverter that communicates with an output of the comparator module andanother input of the difference amplifier module.

In other features, a filter and decimation module receives an output ofthe comparator module. At least one of the difference amplifier module,the integrator module and the comparator module includes thedifferential transimpedance amplifier.

A differential transimpedance amplifier circuit comprises firstamplifying means for amplifying having a first inverting input, a firstnon-inverting input, a first inverting output and a first non-invertingoutput; second amplifying means for amplifying having a second invertinginput, a second non-inverting input, a second inverting output and asecond non-inverting output, wherein the second inverting outputcommunicates with the first non-inverting input and the secondnon-inverting output communicates with the first inverting input; firstfeedback means for providing feedback that communicates with the firstnon-inverting input and the first inverting output; second feedbackmeans for providing feedback that communicates with the first invertinginput and the first non-inverting output; third feedback means forproviding feedback that communicates with the second inverting input andthe first inverting output; and fourth feedback means for providingfeedback that communicates with the first non-inverting input and thefirst non-inverting output.

In other features, the third and fourth feedback means comprise firstand second resistance means for providing resistance, respectively. Thethird and fourth feedback means comprise first and second capacitancesfor providing capacitance, respectively. The first and second feedbackmeans comprise first and second resistance means for providingresistance, respectively. The first and second feedback means comprisefirst and second capacitance means for providing capacitance,respectively. The first and second feedback means each comprise firstresistance means for providing resistance in series with inductancemeans for providing inductance and second resistance means for providingresistance that are in parallel with a capacitance means for providingcapacitance. The capacitance means provides a variable capacitance. Thefirst and second feedback means each comprise resistance means forproviding resistance in parallel with capacitance means for providingcapacitance. The capacitance means provides a variable capacitance. Thefirst and second feedback means each comprise first resistance means forproviding resistance in series with inductance means for providinginductance and that are in parallel with capacitance means for providingcapacitance and second resistance means for providing resistance. Thecapacitance means provides a variable capacitance. The first and secondamplifying means include transconductance amplifiers.

A single-nested transimpedance amplifier circuit comprises thirdamplifying means for amplifying having a third inverting input, a thirdnon-inverting input, a third inverting output and a third non-invertingoutput; and the differential transimpedance amplifier circuit. Thesecond inverting input communicates with the third non-inverting outputand the second non-inverting input communicates with the third invertingoutput.

A double-nested differential transimpedance amplifier circuit comprisesa single-nested transimpedance amplifier circuit; and fourth amplifyingmeans for amplifying having a fourth inverting input, a fourthnon-inverting input, a fourth inverting output and a fourthnon-inverting output. The fourth inverting output communicates with thethird non-inverting output and the fourth non-inverting outputcommunicates with the third inverting input.

In other features, fifth feedback means for providing feedbackcommunicates with the fourth inverting output and the first invertingoutput. Sixth feedback means for providing feedback communicates withthe fourth non-inverting output and the first non-inverting output. Thefifth and sixth feedback means comprise first and second resistancemeans for providing resistance, respectively.

A Sigma-Delta analog to digital converter comprises the differentialtransimpedance amplifier. The Sigma-Delta analog to digital converterincludes difference amplifier means for amplifying that includes oneinput that receives an input signal; integrator means for integratingthat communicates with an output of the difference amplifier means;comparator means for comparing that receives an output of the integratormeans; and digital to analog converter means for converting thatcommunicates with an output of the comparator means and another input ofthe difference amplifier means.

In other features, filter and decimation means for filtering anddecimating receives an output of the comparator means. At least one ofthe difference amplifier means, the integrator means and the comparatormeans includes the differential transimpedance amplifier.

A differential transimpedance amplifier circuit comprises a firstoperational amplifier having a first inverting input, a firstnon-inverting input, a first inverting output and a first non-invertingoutput; a second operational amplifier having a second inverting input,a second non-inverting input, a second inverting output and a secondnon-inverting output, wherein the second inverting output communicateswith the first non-inverting input and the second non-inverting outputcommunicates with the first inverting input; a third operationalamplifier having a third inverting input, a third non-inverting input, athird inverting output and a third non-inverting output, wherein thesecond inverting input communicates with the third non-inverting outputand the second non-inverting input communicates with the third invertingoutput; a fourth operational amplifier having a fourth inverting input,a fourth non-inverting input, a fourth inverting output and a fourthnon-inverting output, wherein the fourth inverting output communicateswith the third non-inverting output and the fourth non-inverting outputcommunicates with the third inverting input; a first feedback elementthat communicates with the second non-inverting input and the secondinverting output; a second feedback element that communicates with thesecond inverting input and the second non-inverting output; a thirdfeedback element that communicates with the third non-inverting inputand the first inverting output; a fourth feedback element thatcommunicates with the third inverting input and the first non-invertingoutput; a fifth feedback element that communicates with the fourthinverting input and the first inverting output; and a sixth feedbackelement that communicates with the fourth non-inverting output and thefirst non-inverting output.

In other features, the first and second feedback elements comprise firstand second resistances, respectively. The third and fourth feedbackelements comprise first and second resistances, respectively. The fifthand sixth feedback elements comprise first and second resistances,respectively.

A Sigma-Delta analog to digital converter comprises the differentialtransimpedance amplifier. The Sigma-Delta analog to digital convertercomprises a difference amplifier module that includes one input thatreceives an input signal; an integrator module that communicates with anoutput of the difference amplifier module; a comparator module thatreceives an output of the integrator module; and a digital to analogconverter that communicates with an output of the comparator module andanother input of the difference amplifier module.

In other features, a filter and decimation module receives an output ofthe comparator module. At least one of the difference amplifier module,the integrator module and the comparator module includes thedifferential transimpedance amplifier.

A differential transimpedance amplifier circuit comprises firstamplifying means for amplifying having a first inverting input, a firstnon-inverting input, a first inverting output and a first non-invertingoutput; second amplifying means for amplifying having a second invertinginput, a second non-inverting input, a second inverting output and asecond non-inverting output, wherein the second inverting outputcommunicates with the first non-inverting input and the secondnon-inverting output communicates with the first inverting input; athird amplifying means for amplifying having a third inverting input, athird non-inverting input, a third inverting output and a thirdnon-inverting output, wherein the second inverting input communicateswith the third non-inverting output and the second non-inverting inputcommunicates with the third inverting output; a fourth amplifying meansfor amplifying having a fourth inverting input, a fourth non-invertinginput, a fourth inverting output and a fourth non-inverting output,wherein the fourth inverting output communicates with the thirdnon-inverting output and the fourth non-inverting output communicateswith the third inverting input; a first feedback means for providingfeedback that communicates with the second non-inverting input and thesecond inverting output; a second feedback means for providing feedbackthat communicates with the second inverting input and the secondnon-inverting output; a third feedback means for providing feedback thatcommunicates with the third non-inverting input and the first invertingoutput; a fourth feedback means for providing feedback that communicateswith the third inverting input and the first non-inverting output; afifth feedback means for providing feedback that communicates with thefourth inverting input and the first inverting output; and a sixthfeedback means for providing feedback that communicates with the fourthnon-inverting output and the first non-inverting output.

In other features, the first and second feedback means comprise firstand second resistance means for providing resistance, respectively. Thethird and fourth feedback means comprise first and second resistancemeans for providing resistance, respectively. The fifth and sixthfeedback means comprises first and second resistance means for providingresistance, respectively.

A Sigma-Delta analog to digital converter comprises the differentialtransimpedance amplifier. The Sigma-Delta analog to digital converterincludes difference amplifier means for amplifying that includes oneinput that receives an input signal; integrator means for integratingthat communicates with an output of the difference amplifier means;comparator means for comparing that receives an output of the integratormeans; and digital to analog converter means for converting thatcommunicates with an output of the comparator means and another input ofthe difference amplifier means.

In other features, filter and decimation means for filtering anddecimating receives an output of the comparator means. At least one ofthe difference amplifier means, the integrator means and the comparatormeans includes the differential transimpedance amplifier.

A transimpedance amplifier comprises a first operational amplifierhaving an input and an output. A second operational amplifier has aninput and an output that communicates with the input of the firstoperational amplifier. A first feedback element has one end thatcommunicates with the input of the first operational amplifier andanother end that communicates with the output of the first operationalamplifier, wherein the first feedback element comprises a firstcapacitance. A second feedback element communicates with the input ofthe first operational amplifier and another end that communicates withthe output of the first operational amplifier.

In other features, the second feedback element comprises a firstresistance. The first capacitance includes a variable capacitance. Thefirst feedback element comprises a first resistance in parallel with thefirst capacitance. The second feedback element comprises a firstresistance in series with a first inductance. The first capacitancecomprises a variable capacitance. A first resistance having one end thatcommunicates with the another ends of the first and second feedbackelements and another end that communicates with the output of the secondoperational amplifier. The first feedback element further comprises afirst resistance in series with the first capacitance, and wherein thesecond feedback element comprises a first inductance in parallel with asecond resistance. A differential amplifier comprises the transimpedanceamplifier.

A Sigma-Delta analog to digital converter comprises the differentialtransimpedance amplifier. The Sigma-Delta analog to digital convertercomprises a difference amplifier module that includes one input thatreceives an input signal; an integrator module that communicates with anoutput of the difference amplifier module; a comparator module thatreceives an output of the integrator module; and a digital to analogconverter that communicates with an output of the comparator module andanother input of the difference amplifier module.

In other features, a filter and decimation module receives an output ofthe comparator module. At least one of the difference amplifier module,the integrator module and the comparator module includes thedifferential transimpedance amplifier.

A transimpedance amplifier comprises first amplifying means foramplifying having an input and an output. Second amplifying means foramplifying having an input and an output that communicates with theinput of the first amplifying means. First feedback means for providingfeedback having one end that communicates with the input of the firstamplifying means and another end that communicates with the output ofthe first amplifying means. The first feedback means comprises firstcapacitance means for providing capacitance. Second feedback means forproviding feedback having one end that communicates with the input ofthe first amplifying means and another end that communicates with theoutput of the first amplifying means.

In other features, the second feedback means comprises first resistancemeans for providing resistance. The first capacitance means includesvariable capacitance means for providing a variable capacitance. Thefirst feedback means comprises first resistance means for providingresistance in parallel with the first capacitance means. The secondfeedback means comprises first resistance means for providing resistancein series with first inductance means for providing inductance. Thefirst capacitance means comprises variable capacitance means forproviding a variable capacitance. First resistance means for providingresistance having one end that communicates with the another ends of thefirst and second feedback means and another end that communicates withthe output of the second amplifying means. The first feedback meansfurther comprises first resistance means for providing resistance inseries with the first capacitance means, and wherein the second feedbackmeans comprises first inductance means for providing inductance inparallel with second resistance means for providing resistance. Adifferential transimpedance amplifier comprises the transimpedanceamplifier.

A Sigma-Delta analog to digital converter comprises the differentialtransimpedance amplifier. The Sigma-Delta analog to digital converterincludes difference amplifier means for amplifying that includes oneinput that receives an input signal; integrator means for integratingthat communicates with an output of the difference amplifier means;comparator means for comparing that receives an output of the integratormeans; and digital to analog converter means for converting thatcommunicates with an output of the comparator means and another input ofthe difference amplifier means.

In other features, filter and decimation means for filtering anddecimating receives an output of the comparator means. At least one ofthe difference amplifier means, the integrator means and the comparatormeans includes the differential transimpedance amplifier.

Further areas of applicability of the present invention will becomeapparent from the detailed description provided hereinafter. It shouldbe understood that the detailed description and specific examples, whileindicating the preferred embodiment of the invention, are intended forpurposes of illustration only and are not intended to limit the scope ofthe invention.

BRIEF DESCRIPTION OF THE DRAWINGS

The present invention will become more fully understood from thedetailed description and the accompanying drawings, wherein:

FIGS. 1 and 2 are basic circuit architectures for a current-to-voltageTIA according to the prior art;

FIGS. 3 and 4 are basic circuit architectures for a voltage-to-voltageTIA according to the prior art;

FIG. 5 is a basic circuit architecture for a differential configurationof a TIA according to the prior art;

FIG. 6 shows an optical sensor, including a photodiode coupled to a TIA,according to the prior art;

FIG. 7 is a first-order nested TIA according to the present invention;

FIG. 8 is a second-order nested TIA according to the present invention;

FIG. 9 is an nth-order nested TIA according to the present invention;

FIG. 10 is a first-order nested TIA in a differential configurationaccording to the present invention;

FIG. 11 is an nth-order nested TIA in a differential configurationaccording to the present invention;

FIG. 12 is a graph of exemplary gain-bandwidth characteristics for aTIA;

FIG. 13 is a graph of an exemplary gain-bandwidth characteristic for afirst-order nested TIA;

FIG. 14 is a graph of an exemplary gain-bandwidth characteristic for asecond-order nested TIA;

FIG. 15 is a first-order nested TIA with capacitive cancellation ofinput parasitic capacitance according to the present invention;

FIG. 16 is a second-order nested TIA with capacitive cancellation ofinput parasitic capacitance according to the present invention;

FIG. 17 is an nth-order nested TIA with capacitive cancellation of inputparasitic capacitance according to the present invention;

FIG. 18 is a first-order nested TIA in a differential configuration withcapacitive cancellation of input parasitic capacitance according to thepresent invention;

FIG. 19 is a second order nested TIA in a differential configurationwith capacitive cancellation of input parasitic capacitance according tothe present invention;

FIG. 20 illustrates the first order nested TIA of FIG. 7 with additionalfeedback resistance;

FIG. 21 illustrates a second order nested TIA of FIG. 8 with additionalfeedback resistance;

FIG. 22 illustrates the first order nested TIA of FIG. 15 withadditional feedback resistance;

FIG. 23 illustrates the first order nested TIA of FIG. 7 with anadditional input capacitance, feedback capacitance, and feedbackresistance;

FIG. 24 illustrates the first order differential mode TIA of FIG. 10with an additional input capacitance, feedback capacitance, and feedbackresistance;

FIG. 25 illustrates an exemplary disk drive system including apreamplifier with a nested TIA according to the present invention.

FIG. 26 illustrates the first order nested TIA of FIG. 7 including anopamp of a first configuration;

FIG. 27 illustrates the differential first-order nested TIA of FIG. 10including an differential opamp of the first configuration;

FIG. 28 illustrates the first order nested TIA of FIG. 26 including anopamp of a second configuration;

FIG. 29 illustrates the differential first-order nested TIA of FIG. 27including an differential opamp of the second configuration;

FIG. 30 illustrates the differential first-order nested TIA of FIG. 10including a differential opamp in a push-pull configuration;

FIGS. 31-33 show a family of gain curves for first and second stages ofnested TIAs;

FIG. 34 shows a functional block diagram of a power supply for nestedTIAs;

FIG. 35 illustrates and exemplary LED drive circuit using the powersupply of FIG. 34;

FIG. 36 is a simplified schematic view of a differential single-nestedtransimpedance amplifier according to one aspect of the disclosure;

FIG. 37 is a simplified schematic view of a differential double-nestedtransimpedance amplifier according to a second embodiment of thedisclosure;

FIG. 38 is a simplified schematic view of a differential amplifiernested according to a third embodiment of the disclosure;

FIGS. 39A and 39B are schematic views of differential and single-endedtransimpedance amplifiers, respectively, having a compensation capacitorin a feedback loop;

FIGS. 40A and 40B are schematic views of differential and single-endednested transimpedance amplifiers, respectively, having an LC tankcircuit;

FIGS. 41 and 41B are schematic views of differential and single-endedtransimpedance amplifiers, respectively, having an LC tank circuit andresistors in the feedback loops according to the present disclosure;

FIG. 42 is a schematic view of an alternative embodiment of atransimpedance amplifier having an LC tank circuit;

FIG. 43A is a functional block diagram of a hard disk drive;

FIG. 43B is a functional block diagram of a digital versatile disk(DVD);

FIG. 43C is a functional block diagram of a high definition television;

FIG. 43D is a functional block diagram of a vehicle control system;

FIG. 43E is a functional block diagram of a cellular phone;

FIG. 43F is a functional block diagram of a set top box;

FIG. 43G is a functional block diagram of a media player; and

FIG. 44 is a functional block diagram of a Delta-Sigma analog to digitalconverter (ADC).

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

The following description of the preferred embodiment(s) is merelyexemplary in nature and is in no way intended to limit the invention,its application, or uses.

The present invention addresses the need for increasing thegain-bandwidth product of TIAs. Improvements in the gain-bandwidthproduct are achievable by “nesting” a TIA within another TIA. In otherwords, additional circuit elements such as feedback resistors,capacitors and/or opamps are added on the input and/or output sides ofthe TIA. In FIGS. 15-17, capacitive cancellation of the input parasiticcapacitance is provided. In FIGS. 20-24, additional feedback resistanceis provided. In FIGS. 23 and 24, input and/or feedback capacitance isprovided.

Referring now to FIGS. 7, 8, and 9, a “nested” TIA is constructed byadding opamps, feedback resistors and/or capacitors to a zero-order TIA.In FIGS. 10 and 11, a nested TIA may also be constructed to operate in adifferential mode.

Referring back to FIG. 7, a first-order nested TIA 700 is shown.Reference numbers from FIG. 4 are used in FIG. 7 to identify similarelements. The TIA 700 includes a conventional TIA 705 (also referred toherein as a “zero-order” TIA), an opamp 710, and a feedback resistor715. The feedback resistor 715 may be a standard fixed-value resistor, anonlinear variable resistor, or an MOS resistor. A capacitor 720 is alsoconnected between an input of the TIA 700 and ground (or virtualground).

By nesting the TIA in this manner, improvements in the gain-bandwidthproduct may be realized. For example, the first-order nested TIA 700that uses MOS transistors may achieve a bandwidth that is 10%-20% of thethreshold frequency f_(T). This range represents a bandwidth that isapproximately five to ten times greater than the bandwidth of thecorresponding zero-order TIA.

Referring now to FIGS. 12 and 13, graphs illustrating characteristicgain-bandwidth curves for a zero-order TIA and a first-order nested TIA,respectively, are shown. In general, a higher value of gain isassociated with a lower value of bandwidth, and a lower value of gain isassociated with a higher value of bandwidth. The gain A, defined as theoutput voltage Δv_(o) divided by the input voltage Δv_(i), is typicallyon the order of a few hundred or a few thousand (i.e., approximately10²-10³). A typical range of threshold frequency (f_(T)) values for a0.13 μm CMOS process is 30 GHz-40 GHz.

In FIG. 12, three exemplary characteristic curves are shown. A high gainvalue yields a bandwidth value of approximately 1 GHz. A medium gainvalue increases the bandwidth to approximately 2 GHz. Other values ofgain and bandwidth are possible. For example, a TIA may have acharacteristic gain value that is higher than the maximum shown in FIG.12 and a bandwidth that is less than 1 GHz. A TIA may have acharacteristic gain value that is lower than the minimum gain valueshown in FIG. 12 and a bandwidth that is greater than 2 GHz. As can beappreciated, the bandwidth varies as an inverse function of gain. Thisfunction may be referred to as the “spread”. The spread is greater forTIAs using MOS transistors than for TIAs using bipolar junctiontransistors (BJTs). Thus, the need to improve the TIA bandwidthperformance is more pronounced with MOS transistors than with BJTtransistors.

The exemplary bandwidth values shown in FIG. 12 do not define upper andlower bandwidth bounds. In many practical applications, bandwidths onthe order of 1 GHz or 2 GHz are too low. Many applications, such as anOC192 fiber optic receiver, require bandwidths on the order of 10 GHz.Preamplifiers for high-speed hard disk drives also typically requirebandwidths that are on the order of several GHz. Referring now to FIG.13, a first-order nested TIA at a typical gain value may have abandwidth of approximately 10 GHz.

Referring now to FIG. 8, a second-order nested TIA 800 builds upon thefirst-order nested TIA 700. Reference numbers from FIGS. 4 and 7 areused in FIG. 8 to identify similar elements. The second-order nested TIA800 includes an opamp 805 at the input of the first-order nested TIA 700and an opamp 810 at the output of the first-order nested TIA 700. Anadditional feedback resistor 815 is also added across the input of theopamp 805 and the output of the opamp 810. An exemplary gain-bandwidthcurve that is produced using the second-order nested TIA 800 is shown inFIG. 14. For a typical gain value, a bandwidth of approximately 20 GHzmay be achieved.

Referring now to FIG. 9, higher-order nested TIAs may be constructed byadding additional opamps and feedback resistors. Reference numbers fromFIGS. 4, 7 and 8 are used in FIG. 9 to identify similar elements. Forexample, a third-order nested TIA 900 includes opamps 905 and 910 andfeedback resistor 915. It is possible to achieve higher values of eithergain or bandwidth (or both) by repeating the technique of the presentinvention. However, the efficiency of the circuit decreases asadditional nesting levels are added due to parasitic noise and increasedpower dissipation. In general, either the first-order nested TIA or thesecond-order nested TIA will usually provide sufficient performance.

Referring now to FIG. 10, a differential mode first-order nested TIA1000 is shown. Reference numbers from FIG. 5 are used in FIG. 10 toidentify similar elements. An opamp 1002 is connected to the outputs ofthe opamp 504. Feedback resistors 1006 and 1008 are connected to inputsof the differential mode TIA 500 and to outputs of the opamp 1002. Thegain-bandwidth product of the TIA is increased.

Referring now to FIG. 11, a differential mode nth-order nested TIA 1100is constructed in a manner that is similar to the nth-order nested TIAof FIG. 9. Reference numbers from FIGS. 5 and 10 are used in FIG. 11 toidentify similar elements. Additional opamps 1104 and 1108 and feedbackresistors 1112 and 1114 are connected in a similar manner. Thegain-bandwidth characteristics for differential mode TIAs aresubstantially similar to the gain-bandwidth characteristics shown inFIGS. 12-14.

It is noted that the opamps used in the nested TIA may employ eitherbipolar junction transistors (BJTs), such as gallium-arsenide (GaAs)transistors, or metal-oxide-semiconductor (MOS) transistors, such asCMOS or BICMOS transistors. The preferred embodiments of the inventionuse MOS transistors due to practical considerations such as ease ofmanufacture and better power consumption characteristics.

Referring now to FIG. 15, the first order nested TIA 700 is shown withadditional feedback capacitance C₁, which substantially cancels effectsof an input capacitance C_(P1) at the input of the opamp 415. Thefeedback capacitance C₁ has a first end that communicates with an inputof the opamp 415 and a second end that communicates with an output ofthe opamp 425.

Referring now to FIG. 16, the second order nested TIA 800 of FIG. 8 isshown with additional feedback capacitances C₁ and C₂, whichsubstantially cancel effects of input capacitances C_(P1) and C_(P2) atthe inputs of opamps 415 and 805, respectively. The feedback capacitanceC₁ has a first end that communicates with an input of the opamp 415 anda second end that communicates with an output of the opamp 425. Thefeedback capacitance C₂ has a first end that communicates with an inputof the opamp 805 and a second end that communicates with an output ofthe opamp 710.

Referring now to FIG. 17, the nth order nested TIA of FIG. 9 is shownwith additional feedback capacitances C₁, C₂, . . ., and C_(N), whichsubstantially cancel effects of input capacitances C_(P1), C_(P2), . .., and C_(PN) at the inputs of opamps 415, 805 and 905, respectively.The feedback capacitance C₁ has a first end that communicates with aninput of the opamp 415 and a second end that communicates with an outputof the opamp 425. The feedback capacitance C₂ has a first end thatcommunicates with an input of the opamp 805 and a second end thatcommunicates with an output of the opamp 710. The feedback capacitanceC_(N) has a first end that communicates with an input of the opamp 905and a second end that communicates with an output of the opamp 810.

Referring now to FIG. 18, the first order nested differential mode TIA1000 is shown with additional feedback capacitors C_(1A) and C_(1B),which substantially cancel effects of input parasitic capacitancesC_(P1) and C_(P2) at the inputs of the differential mode opamp 502. Thefeedback capacitance C_(1A) has a first end that communicates with aninput of the differential mode opamp 502 and a second end thatcommunicates with an output of the differential mode opamp 504. In FIG.19, additional capacitances C_(2A) and C_(2B) are added to a secondorder differential mode TIAs in a similar manner to offset parasiticcapacitances C_(P2A) and C_(P2B). Higher order circuits use a similarapproach.

Referring back to FIG. 20, the first order nested TIA of FIG. 7 is shownwith additional feedback resistance 2010. The feedback resistance 2010has a first end that communicates with an input of the opamp 710. Asecond end of the resistance 2010 communicates with an output of theopamp 710.

Referring now to FIG. 21, the second order nested TIA of FIG. 8 is shownwith additional feedback resistance 2110. The feedback resistance 2110has a first end that communicates with an input of the opamp 810. Asecond end of the resistance 2110 communicates with an output of theopamp 810.

Referring now to FIG. 22, the first order nested TIA of FIG. 15 is shownwith additional feedback resistance 2210. The feedback resistance 2210has a first end that communicates with an input of the opamp 710. Asecond end of the resistance 2210 communicates with an output of theopamp 710.

Referring now to FIG. 23, the first order nested TIA of FIG. 7 is shownwith input capacitance C_(IN), feedback capacitance C_(FB), and feedbackresistance 2310. The input capacitance C_(IN) has a first end thatreceives an input signal for the nested TIA 700 and a second end thatcommunicates with an input of opamp 415. The feedback capacitance C_(FB)has a first end that communicates with an input of opamp 415 and asecond end that communicates with one end of resistance 715.

The additional feedback resistances, input capacitances, and/or feedbackcapacitances can also be added to the differential mode nested TIA.Referring now to FIG. 24, the first order differential mode nested TIAof FIG. 10 is shown with first and second input capacitances C_(IN1),and C_(IN2), first and second feedback capacitances C_(FB1) and C_(FB2),and feedback resistances 2410 and 2412. The input capacitances C_(IN1),and C_(IN2) have first ends that receive input signals for the nesteddifferential mode TIA and second ends that communicate with inputs ofopamp 502. The feedback capacitances C_(FB1) and C_(FB2) have first endsthat communicate with inputs of opamp 502 and second ends thatcommunicate with first ends of resistances 1006 and 1008, respectively.First and second feedback resistances 2410 and 2412 have first ends thatare connected to inputs and second ends that are connected to outputs ofdifferential mode opamp 1002.

As can be appreciated, the feedback capacitances (FIGS. 5-19), feedbackresistances (FIGS. 20-24), and input and feedback capacitances (FIGS. 23and 24) can be used in any combination on first, second, . . . or n^(th)order nested TIA and/or differential mode TIA.

Referring now to FIG. 25, an exemplary disk drive system 2500 is shownto include a disk drive write circuit 2510 that writes to a disk drive2514. A disk drive read circuit 2516 includes a preamp circuit 2518 witha nested TIA or nested differential mode TIA identified at 2520, whichis implemented as described above.

Referring now to FIG. 26, the first-order nested TIA 700 of FIG. 7 isshown including a first implementation of opamp 710. Opamp 710 includesa first transistor 2600 in series with a second transistor 2602. A gateof the first transistor 2600 is driven by the output of the zero-orderTIA 705. A gate of the second transistor 2602 is driven by a biasvoltage V_(B). The signal output of TIA 700 is taken at a nodeconnecting a source of the first transistor 2600 with a drain of thesecond transistor 2602. A first current source 2604 draws current from asource of the second transistor 2602. The opamp 710 can be powered witha drain supply voltage V_(dd2). Power supply options are described belowin more detail.

Referring now to FIG. 27, the differential mode first-order nested TIA1000 of FIG. 10 is shown including a first implementation of opamp 1002.Opamp 1002 includes a first transistor 2700 in communication with asecond transistor 2702. A gate of the first transistor 2700 is driven byone output of the differential zero-order TIA 500. A gate of the secondtransistor 2702 is driven by a bias voltage V_(B). A first signal outputof TIA 1000 is taken at a node connecting a source of the firsttransistor 2600 with a drain of the second transistor 2702. A firstcurrent source 2704 draws current from a source of the second transistor2702.

A third transistor 2706 is in communication with a fourth transistor2708. A gate of the third transistor 2706 is driven by the other outputof the differential zero-order TIA 500. A gate of the fourth transistor2708 is driven by V_(B). A second signal output of TIA 1000 is taken ata node connecting a source of the third transistor 2706 with a drain ofthe fourth transistor 2708. A second current source 2710 draws currentfrom a source of the second transistor 2702. The opamp 1002 can bepowered with a drain supply voltage V_(dd2). Power supply options aredescribed below in more detail. The differential signal output is takenacross the first and second signal outputs at the respective sources offirst and third transistors 2700, 2706.

Referring now to FIG. 28, the first-order nested TIA 700 of FIG. 26 isshown including a second implementation of opamp 710. The secondimplementation includes a second current source 2610 that providescurrent to the drain of the first transistor 2600. The second currentsource 2610 draws current from V_(dd2).

Referring now to FIG. 29, the differential mode first-order nested TIA1000 of FIG. 27 is shown including a second implementation of opamp1002. The second implementation includes a third current source 2712that provides current to the drains of first transistor 2700 and thirdtransistor 2706. The third current source 2712 draws current fromV_(dd2).

Referring now to FIG. 30, the differential mode first-order nested TIA1000 of FIG. 10 is shown including a third implementation of opamp 1002.Opamp 1002 includes a push-pull configuration as shown. The opamp 1002receives a positive bias voltage V_(BP) and a negative bias voltageV_(BN). The differential output signal is taken across nodes V_(out+)and V_(out−).

Referring now to FIGS. 31-33, a family of gain curves is shown. The gaincurves represent typical gain patterns of the various first-order nestedTIAs described above. A logarithmic vertical axis of each graphrepresents gain A=V_(out)/V_(in). A logarithmic horizontal axis of eachgraph represents signal frequency. The graph of FIG. 31 represents again curve 3100 of the various opamps. The opamps provide a lower gainand higher bandwidth than the zero-order TIAs. The opamp gain rolls offat a rate of 20 dB/decade.

The graph of FIG. 32 represents a family of gain curves 3200 for variousTIAs. The gain curve 3200 having the smallest bandwidth corresponds witha zero-order TIA. The gain curves 3200 with higher bandwidths correspondwith increasingly-nested TIAs. The TIAs generally provide a high gainand medium bandwidth when compared to the opamps. The zero-order TIAgain rolls off at a rate of 20 dB/decade.

The graph of FIG. 33 represents a family of gain curves 3300 of thevarious first-order nested TIAs. The gains are relatively flat at thelowest frequencies. As the frequency increases the gains roll off at 20dB/decade due to the gain effects of the opamp as shown in FIG. 31. Asthe frequency continues to increase the gains roll off at 40 dB/decadedue to the combined effects of the opamp and the selected zero-orderTIA.

Referring now to FIG. 34, a functional block diagram is shown of a powersupply arrangement for first-order nested TIAs. The power supplyarrangement provides a TIA chip with three unique voltages levelsdespite providing external connections for two voltages and ground.While FIG. 34 shows the power supply connected to the first-order nestedTIA 700 of FIG. 7, it is understood by those skilled in the art that thepower supply may be used with other single-ended and differentialfirst-order nested TIAs. An analog power supply V_(dda) is associatedwith one of the external connections and provides power to thezero-order TIA. In some embodiments V_(dda) is between about 2.5V and3.3V.

The analog power supply V_(dda) also provides power to a charge pumpmodule 3400. Charge pump module 3400 also receives power from a digitalpower supply V_(ddd). V_(ddd) is associated with the second one of theexternal connections. Charge pump module 3400 can be fabricated on thesame chip as the first-order nested TIAs. In some embodiments V_(ddd) isabout 1.2V. In some embodiments V_(ddd) can be regulated by a voltageregulator module 3402 before being applied to the charge pump module3400. The charge pump module 3400 generates a second digital voltageV_(dd2) that is approximately equal to V_(dda)+V_(ddd). ThereforeV_(dd2)>V_(dda). It is appreciated by those skilled in the art thatV_(dd2) is not exactly equal to V_(dda)+V_(ddd) due to losses and/orinefficiencies inherent in the charge pump module 3400.

Referring now to FIG. 35, an application of the power supply of FIG. 35is shown. V_(dda) is provided by a battery 3500. Battery 3500 can be alithium-ion battery having a voltage between about 2.7V and 4.2V. Alight-emitting diode (LED) communicates with an output of the opamp 710.In some embodiments the LED has a turn-on voltage V_(D) of about 3.5V.The charge pump module 3400 adds V_(dda) from the battery 3500 toV_(ddd) to generate sufficient voltage for driving the LED 3502. SinceV_(ddd) generally provides only about 1.2V it can not be used alone topower the LED 3502. The charge pump module 3400 provides the additionalvoltage from V_(dda) to supply the LED with approximately 3.7V to 4.2V,which is above the 3.5V V_(D). The range of 3.7V to 4.2V accounts forthe losses and/or inefficiencies in the charge pump module 3400 and istherefore not exactly equal to V_(dda)+V_(ddd).

The present disclosure also addresses the need for increasing thegain-bandwidth product of TIAs. Improvements in the gain-bandwidthproduct may be achievable by “nesting” a TIA within another TIA. Inother words, additional circuit elements such as feedback resistances,capacitances and/or opamps are added on the input and/or output sides ofthe TIA.

Referring now to FIG. 36, a nested transimpedance amplifier (TIA)circuit 3600 having an inner TIA 3602 is illustrated. The transimpedanceamplifier 3602 includes a first operational amplifier 3604 and a secondoperational amplifier 3606. Each operational amplifier set forth in thisfigure and the following figures has a non-inverting input andnon-inverting output identified by the absence of the “o” symbol, and aninverting input and inverting output identified by the “o” symbol. Thetransimpedance amplifier 3602 also includes a first feedback resistance3608 that communicates with the non-inverting input and the invertingoutput, and a second resistance 3610 that communicates with theinverting input and the non-inverting output.

The nested transimpedance amplifier 3600 also includes a thirdoperational amplifier 3612 also having an inverting input and output,and a non-inverting input and output. The operational amplifier 3612 hasan inverting output that communicates with the non-inverting input ofamplifier 3606, and a non-inverting output that communicates with theinverting input of amplifier 3606.

A feedback resistance 3614 communicates with the non-inverting output ofamplifier 3612 and the inverting output of amplifier 3604. The invertingoutput of amplifier 3612 communicates with the non-inverting output ofamplifier 3604. That is, resistance 3614 communicates with the invertinginput of amplifier 3606, while resistance 3616 communicates with thenon-inverting input of amplifier 3606.

Referring now to FIG. 37, a double-nested transimpedance amplifier 3700is illustrated. The double-nested transimpedance amplifier includes thetransimpedance amplifier 3602 and the nested transimpedance amplifierstructure 3600 of FIG. 36. Therefore, these common circuit componentswill not be described further. In this embodiment, another amplifier3702 also having inverting and non-inverting inputs and outputs isillustrated. In this embodiment, the inverting output of amplifier 3702communicates with the non-inverting input of amplifier 3612. Thenon-inverting output of amplifier 3702 communicates with the invertinginput of amplifier 3612. A feedback resistance 3704 communicates withthe common node of the inverting output of amplifier 3702 and thenon-inverting input of amplifier 3612. The resistance 3704 is alsocommunicates with the inverting output of amplifier 3604. A secondfeedback resistance 3705 communicates with the common node between thenon-inverting output of amplifier 3702 and the inverting input ofamplifier 3612, and the non-inverting output of amplifier 3604.

By providing the differentials and feedback structures illustrated inFIGS. 36 and 37, fewer inversions for a given level of nesting are setforth. The result is a potentially higher frequency operation from adevice such as that illustrated in FIG. 7. In these examples, thenesting occurs at the output node causing the output distortion to beimproved as the level of nesting increases.

Referring now to FIG. 38, a transimpedance structure 3602 illustrated inFIG. 36 is used in a nested TIA 3800. In this embodiment, an operationalamplifier 3802 has its inverting input communicates with thenon-inverting output of amplifier 3604. The non-inverting input ofamplifier 3802 communicates with the inverting output of amplifier 3604.

Another amplifier 3804 has an inverting output that communicates withthe non-inverting input of amplifier 3606. The non-inverting output ofamplifier 3804 communicates with the inverting input of amplifier 3606.Another operational amplifier 3806 has an inverting output thatcommunicates with the non-inverting input of amplifier 3804 and anon-inverting output that communicates with the inverting input ofamplifier 3804. A first feedback resistance 3808 communicates with thecommon node between the inverting output of amplifier 3804 and thenon-inverting input of amplifier 3606, and the inverting output ofamplifier 3802. Another feedback resistance 3810 communicates with thecommon node of the non-inverting output of amplifier 3804 and theinverting input of amplifier 3606, and the non-inverting output ofamplifier 3802.

A feedback resistance 3812 communicates with the common node between thenon-inverting output of amplifier 3806 and the inverting amplifier 3804,and the inverting output of amplifier 3802. Another resistance 3814communicates with the node between inverting output of amplifier 3806and the non-inverting input of amplifier 3804, and the non-invertingoutput of 3802.

Different types of nesting may be performed to build a higher ordernested transimpedance amplifier. The amplifier 3802 is not important asfar as nesting is concerned. If the input of the circuit is currentinstead of voltage, amplifier 3806 may not be required.

Referring now to FIGS. 39A and 39B, differential and single-endedtransimpedance amplifiers having capacitive feedback are shown,respectively. In FIG. 39A, a differential transimpedance amplifier 3900,which is similar to the transimpedance amplifier 3602 of FIG. 36, isillustrated having a first capacitance 3902 in parallel with resistance3608 and a second capacitance 3904 in parallel with resistance 3610. Inthis embodiment, the frequency response or the stability of thetransimpedance network may be improved by including the capacitances3902 and 3904. As can be appreciated, the capacitances can be replacedby inductances if desired.

In FIG. 39B, a single-ended transimpedance amplifier 3900′ is shown thatis similar to the differential configuration shown in FIG. 39A. In FIG.39B, similar elements are labeled with a prime symbol “′”. Thetransconductance g_(m) of the amplifiers 3604′ and/or 3606′ may benegative and/or the signals may be coupled to inverting input(s) of theamplifiers 3604′ and/or 3606′.

Referring now to FIGS. 40A and 40B, an LC tank circuit is included inthe feedback of differential and single-ended transimpedance amplifiers,respectively. In FIG. 40A, a differential transimpedance amplifier 4000is shown. In this embodiment, a first operational amplifier 4002 has anon-inverting input communicates with an inverting output of amplifier4004. The inverting input of amplifier 4002 communicates with thenon-inverting output of amplifier 4004. A feedback element 4006communicates with the common node of the non-inverting input ofamplifier 4002 and the inverting output of amplifier 4004, and theinverting output of amplifier 4002. Likewise, a second feedback element4008 communicates with the common node of the inverting input ofamplifier 4002 and the non-inverting output of amplifier 4004, and thenon-inverting output of amplifier 4002.

The feedback element 4006 includes a resistance 4010, a seriescombination of a resistance 4012, and an inductance 4014. In someimplementations, the inductance 4014 can be a variable inductance. Avariable capacitance 4016 is coupled in parallel with the seriescombination of the resistance 4012 and the inductance 4014. Thisparallel combination is coupled in series with the resistance 4010.Likewise, the feedback element 4008 is configured in a similar way witha resistance 4020, a second resistance 4022 in series with an inductance4024, and a variable capacitance 4026.

The variable capacitances 4016 and 4026 are used to illustrate thatvarious resonant frequencies of the LC tank circuit may be adjusted bychanging the capacitance values. In an actual embodiment, a fixedcapacitance set to the desired residence frequency may be used. Thecircuit 4000 may be suitable for use as an RF amplifier in a TV tuner inwhich it is desirable to include an ultra-wide band of operation (e.g.,50 MHz-1 GHz). The circuit amplifies the wanted signal more than theunwanted signal by taking advantage of the LC tank in combination withthe transimpedance amplifier property of the wide-band operation. Theparallel LC tank circuit causes the feedback network to have highimpedance at a resonance frequency of the LC tank circuit.

The structure illustrated in FIG. 40 may also be nested in an amplifierstructure illustrated above. With each subsequent nesting, only thesignal frequency of interest is amplified so that the nesting behavioris effective at the residence frequency of the LC tank elements. Becauseof this, the selectivity of the nested LC tank circuit transimpedanceamplifier is significantly improved while the out-of-band signals arenot amplified. This improves the distortion performance of the amplifierby not amplifying the unwanted signals. At the same time, in-bandsignals are amplified with extremely low distortion because of thenature of the nesting transimpedance amplifier.

In FIG. 40B, a single-ended transimpedance amplifier 4000′ is shown thatis similar to the differential configuration shown in FIG. 40A. In FIG.40B, similar elements are labeled with a prime symbol “′”. Thetransconductance g_(m) of the amplifiers 4002′ and/or 4004′ may benegative and/or the signals may be coupled to inverting input(s) of theamplifiers 4002′ and/or 4004′.

Referring now to FIGS. 41A and 41B, a schematic view of anotherembodiment of differential and single-ended transimpedance amplifiersare shown, respectively. In FIG. 41A, a differential transimpedanceamplifier 4100 using an LC circuit is illustrated. In this embodiment, afirst operational amplifier 4102 communicates with a second amplifier4104. An inverting output of amplifier 4104 communicates with anon-inverting input of amplifier 4102. A non-inverting output ofamplifier 4104 communicates with an inverting input of amplifier 4102. Afirst LC circuit 4106 communicates with the non-inverting input ofamplifier 4102 and the inverting output of amplifier 4102. A second LCcircuit 4108 communicates with the inverting input and the non-invertingoutput of amplifier 4102.

LC circuit 4106 includes an inductance 4110 in series with a resistance4112. The LC circuit 4106 also includes a capacitance 4114 in serieswith a resistance 4116. The series combination of the capacitance 4114and resistance 4116 is in parallel with the series combination of theinductance 4110 and the resistance 4112.

The LC circuit 4108 is configured in a similar manner to LC circuit4106. The LC circuit 4108 includes an inductance 4120 in series with aresistance 4122. A capacitance 4124 is in series with a resistance 4126.The series combination of the inductance 4120 and resistance 4122 is inparallel with the series combination of the capacitance 4124 and theresistance 4126.

By providing a resistance in parallel with the LC tank circuit, asillustrated in FIG. 40, or adding a resistance to both the inductanceand capacitance, oscillations of the circuit are avoided. The extraresistance, as compared to FIG. 40, prevents the polarity of theamplifier from changing at high frequencies. This is used to preventfeedback operation within the nested transimpedance structure.

In FIG. 41B, a single-ended transimpedance amplifier 4100′ is shown thatis similar to the differential configuration shown in FIG. 41A. In FIG.41B, similar elements are labeled with a prime symbol “′”. Thetransconductance g_(m) of the amplifiers 4102′ and/or 4104′ may benegative and/or the signals may be coupled to inverting input(s) of theamplifiers 4102′ and/or 4104′.

Referring now to FIG. 42, an integrator 4200 that is formed using anested transimpedance amplifier is illustrated. This embodiment isidentical to the double-nested transimpedance amplifier illustrated inFIG. 37, except that resistances 3704 and 3705 have been replaced withcapacitances 4202 and 4204.

The integrator 4200 has a high bandwidth due to the transimpedanceconfiguration. The impedance output is low even at high frequencies.Because of the low output impedance, the integrator 4200 may be usefulto drive large capacitive loads. One application of the integrator 4200may be in a Sigma-Delta analog-to-digital converter that operates atgigahertz over sampling frequencies.

Referring now to FIGS. 43A-43G, various exemplary implementations of thepresent disclosure are shown. Referring now to FIG. 43A, the presentdisclosure can be implemented in amplifiers and/or integrators of a harddisk drive 4300. The present disclosure may implement and/or beimplemented in either or both signal processing and/or control circuitsand/or a power supply 4303, which are generally identified in FIG. 43Aat 4302. In some implementations, the signal processing and/or controlcircuit 4302 and/or other circuits (not shown) in the HDD 4300 mayprocess data, perform coding and/or encryption, perform calculations,and/or format data that is output to and/or received from a magneticstorage medium 4306.

The HDD 4300 may communicate with a host device (not shown) such as acomputer, mobile computing devices such as personal digital assistants,cellular phones, media or MP3 players and the like, and/or other devicesvia one or more wired or wireless communication links 4308. The HDD 4300may be connected to memory 4309 such as random access memory (RAM), lowlatency nonvolatile memory such as flash memory, read only memory (ROM)and/or other suitable electronic data storage.

Referring now to FIG. 43B, the present disclosure can be implemented inamplifiers and/or integrators of a digital versatile disc (DVD) drive4310. The present disclosure may implement and/or be implemented ineither or both signal processing and/or control circuits, which aregenerally identified in FIG. 43B at 4312, mass data storage of the DVDdrive 4310 and/or a power supply 4313. The signal processing and/orcontrol circuit 4312 and/or other circuits (not shown) in the DVD 4310may process data, perform coding and/or encryption, performcalculations, and/or format data that is read from and/or data writtento an optical storage medium 4316. In some implementations, the signalprocessing and/or control circuit 4312 and/or other circuits (not shown)in the DVD 4310 can also perform other functions such as encoding and/ordecoding and/or any other signal processing functions associated with aDVD drive.

The DVD drive 4310 may communicate with an output device (not shown)such as a computer, television or other device via one or more wired orwireless communication links 4317. The DVD 4310 may communicate withmass data storage 4318 that stores data in a nonvolatile manner. Themass data storage 4318 may include a hard disk drive (HDD). The HDD mayhave the configuration shown in FIG. 43A. The HDD may be a mini HDD thatincludes one or more platters having a diameter that is smaller thanapproximately 1.8″. The DVD 4310 may be connected to memory 4319 such asRAM, ROM, low latency nonvolatile memory such as flash memory and/orother suitable electronic data storage.

Referring now to FIG. 43C, the present disclosure can be implemented inamplifiers and/or integrators of a high definition television (HDTV)4320. The present disclosure may implement and/or be implemented ineither or both signal processing and/or control circuits, which aregenerally identified in FIG. 43E at 4322, a WLAN interface, mass datastorage of the HDTV 4320 and/or a power supply 4323. The HDTV 4320receives HDTV input signals in either a wired or wireless format andgenerates HDTV output signals for a display 4326. In someimplementations, signal processing circuit and/or control circuit 4322and/or other circuits (not shown) of the HDTV 4320 may process data,perform coding and/or encryption, perform calculations, format dataand/or perform any other type of HDTV processing that may be required.

The HDTV 4320 may communicate with mass data storage 4327 that storesdata in a nonvolatile manner such as optical and/or magnetic storagedevices. At least one HDD may have the configuration shown in FIG. 43Aand/or at least one DVD may have the configuration shown in FIG. 43B.The HDD may be a mini HDD that includes one or more platters having adiameter that is smaller than approximately 1.8″. The HDTV 4320 may beconnected to memory 4328 such as RAM, ROM, low latency nonvolatilememory such as flash memory and/or other suitable electronic datastorage. The HDTV 4320 also may support connections with a WLAN via aWLAN network interface 4329.

Referring now to FIG. 43D, the present disclosure may implement and/orbe implemented in amplifiers and/or integrators of a control system of avehicle 4330, a WLAN interface, mass data storage of the vehicle controlsystem and/or a power supply 4333. In some implementations, the presentdisclosure implement a powertrain control system 4332 that receivesinputs from one or more sensors such as temperature sensors, pressuresensors, rotational sensors, airflow sensors and/or any other suitablesensors and/or that generates one or more output control signals such asengine operating parameters, transmission operating parameters, and/orother control signals.

The present disclosure may also be implemented in other control systems4340 of the vehicle 4330. The control system 4340 may likewise receivesignals from input sensors 4342 and/or output control signals to one ormore output devices 4344. In some implementations, the control system4340 may be part of an anti-lock braking system (ABS), a navigationsystem, a telematics system, a vehicle telematics system, a lanedeparture system, an adaptive cruise control system, a vehicleentertainment system such as a stereo, DVD, compact disc and the like.Still other implementations are contemplated.

The powertrain control system 4332 may communicate with mass datastorage 4346 that stores data in a nonvolatile manner. The mass datastorage 4346 may include optical and/or magnetic storage devices forexample hard disk drives HDD and/or DVDs. At least one HDD may have theconfiguration shown in FIG. 43A and/or at least one DVD may have theconfiguration shown in FIG. 43B. The HDD may be a mini HDD that includesone or more platters having a diameter that is smaller thanapproximately 1.8″. The powertrain control system 4332 may be connectedto memory 4347 such as RAM, ROM, low latency nonvolatile memory such asflash memory and/or other suitable electronic data storage. Thepowertrain control system 4332 also may support connections with a WLANvia a WLAN network interface 4348. The control system 4340 may alsoinclude mass data storage, memory and/or a WLAN interface (all notshown).

Referring now to FIG. 43E, the present disclosure can be implemented inamplifiers and/or integrators of a cellular phone 4350 that may includea cellular antenna 4351. The present disclosure may implement and/or beimplemented in either or both signal processing and/or control circuits,which are generally identified in FIG. 43E at 4352, a WLAN interface,mass data storage of the cellular phone 4350 and/or a power supply 4353.In some implementations, the cellular phone 4350 includes a microphone4356, an audio output 4358 such as a speaker and/or audio output jack, adisplay 4360 and/or an input device 4362 such as a keypad, pointingdevice, voice actuation and/or other input device. The signal processingand/or control circuits 4352 and/or other circuits (not shown) in thecellular phone 4350 may process data, perform coding and/or encryption,perform calculations, format data and/or perform other cellular phonefunctions.

The cellular phone 4350 may communicate with mass data storage 4364 thatstores data in a nonvolatile manner such as optical and/or magneticstorage devices for example hard disk drives HDD and/or DVDs. At leastone HDD may have the configuration shown in FIG. 43A and/or at least oneDVD may have the configuration shown in FIG. 43B. The HDD may be a miniHDD that includes one or more platters having a diameter that is smallerthan approximately 1.8″. The cellular phone 4350 may be connected tomemory 4366 such as RAM, ROM, low latency nonvolatile memory such asflash memory and/or other suitable electronic data storage. The cellularphone 4350 also may support connections with a WLAN via a WLAN networkinterface 4368.

Referring now to FIG. 43F, the present disclosure can be implemented inamplifiers and/or integrators of a set top box 4380. The presentdisclosure may implement and/or be implemented in either or both signalprocessing and/or control circuits, which are generally identified inFIG. 43F at 4384, a WLAN interface, mass data storage of the set top box4380 and/or a power supply 4383. The set top box 4380 receives signalsfrom a source such as a broadband source and outputs standard and/orhigh definition audio/video signals suitable for a display 4388 such asa television and/or monitor and/or other video and/or audio outputdevices. The signal processing and/or control circuits 4384 and/or othercircuits (not shown) of the set top box 4380 may process data, performcoding and/or encryption, perform calculations, format data and/orperform any other set top box function.

The set top box 4380 may communicate with mass data storage 4390 thatstores data in a nonvolatile manner. The mass data storage 4390 mayinclude optical and/or magnetic storage devices for example hard diskdrives HDD and/or DVDs. At least one HDD may have the configurationshown in FIG. 43A and/or at least one DVD may have the configurationshown in FIG. 43B. The HDD may be a mini HDD that includes one or moreplatters having a diameter that is smaller than approximately 1.8″. Theset top box 4380 may be connected to memory 4394 such as RAM, ROM, lowlatency nonvolatile memory such as flash memory and/or other suitableelectronic data storage. The set top box 4380 also may supportconnections with a WLAN via a WLAN network interface 4396.

Referring now to FIG. 43G, the present disclosure can be implemented inamplifiers and/or integrators of a media player 4400. The presentdisclosure may implement and/or be implemented in either or both signalprocessing and/or control circuits, which are generally identified inFIG. 43G at 4404, a WLAN interface, mass data storage of the mediaplayer 4400 and/or a power supply 4403. In some implementations, themedia player 4400 includes a display 4407 and/or a user input 4408 suchas a keypad, touchpad and the like. In some implementations, the mediaplayer 4400 may employ a graphical user interface (GUI) that typicallyemploys menus, drop down menus, icons and/or a point-and-click interfacevia the display 4407 and/or user input 4408. The media player 4400further includes an audio output 4409 such as a speaker and/or audiooutput jack. The signal processing and/or control circuits 4404 and/orother circuits (not shown) of the media player 4400 may process data,perform coding and/or encryption, perform calculations, format dataand/or perform any other media player function.

The media player 4400 may communicate with mass data storage 4410 thatstores data such as compressed audio and/or video content in anonvolatile manner. In some implementations, the compressed audio filesinclude files that are compliant with MP3 format or other suitablecompressed audio and/or video formats. The mass data storage may includeoptical and/or magnetic storage devices for example hard disk drives HDDand/or DVDs. At least one HDD may have the configuration shown in FIG.43A and/or at least one DVD may have the configuration shown in FIG.43B. The HDD may be a mini HDD that includes one or more platters havinga diameter that is smaller than approximately 1.8″. The media player4400 may be connected to memory 4414 such as RAM, ROM, low latencynonvolatile memory such as flash memory and/or other suitable electronicdata storage. The media player 4400 also may support connections with aWLAN via a WLAN network interface 4416. Still other implementations inaddition to those described above are contemplated.

Referring now to FIG. 44, a Sigma Delta analog to digital converter(ADC) module 4510 is shown. The Sigma Delta ADC module 2810 includes adifference amplifier module 4514 that receives an analog input signal.An output of the difference amplifier module 4514 is input to anintegrator module 4518. An output of the integrator module 4518 is oneinput of a comparator module 4520. Another input of the comparatormodule 4520 may be connected to a reference potential such as ground. Anoutput of the comparator module 4520 is input to a filter and decimatormodule 4524, which outputs a digital signal. The output of thecomparator module 4520 is input to a digital to analog converter (DAC)module 4528. The DAC module 4528 may be a 1-bit DAC. An output of theDAC module 4528 is input to an inverting input of the differenceamplifier module 4514.

In use, the output of the DAC module 4528 is subtracted from the inputsignal. The resulting signal is integrated by the integrator module4518. The integrator output voltage is converted to a single bit digitaloutput (1 or 0) by the comparator module 4520. The resulting bit becomesan input to the DAC module 4528. This closed-loop process may be carriedout at a very high oversampled rate. The digital data output by thecomparator module is a stream of ones and zeros and the value of thesignal is proportional to the density of ones output by the comparatormodule. For an increasing value, the density of ones increases. For adecreasing value, the density of ones decreases. By summing the errorvoltage, the integrator acts as a lowpass filter to the input signal anda highpass filter to the quantization noise. The bit stream is digitallyfiltered by the filter and decimator module to provide a binary-formatoutput.

As can be appreciated, the TIA amplifiers described in the embodimentsset forth above may be used to implement one or more of the differenceamplifier module, the integrator module and the comparator module in theSigma Delta DAC module.

Those skilled in the art can now appreciate from the foregoingdescription that the broad teachings of the present invention can beimplemented in a variety of forms. Therefore, while this invention hasbeen described in connection with particular examples thereof, the truescope of the invention should not be so limited since othermodifications will become apparent to the skilled practitioner upon astudy of the drawings, the specification and the following claims.

1. A nested transimpedance amplifier (TIA) circuit, comprising: azero-order TIA having an input and an output; a first operationalamplifier (opamp) having an output and an input that communicates withsaid output of said zero-order TIA; a first power supply input forapplying a first voltage to the zero-order TIA; a second power supplyinput for receiving a second voltage; and a charge pump module thatdevelops a third voltage based on the first voltage and the secondvoltage, wherein the third voltage is applied to the opamp.
 2. Thenested TIA circuit of claim 1 wherein the zero-order TIA comprises: afirst opamp including a first input and a first output; a second opampincluding second input and a second output, wherein the second inputcommunicates with the first output; and a resistance including one endthat communicates with the second output and a second end thatcommunicates with the second input.
 3. The TIA circuit of claim 1further comprising a voltage regulator that regulates the secondvoltage.
 4. The TIA circuit of claim 1 further comprising alight-emitting diode in communication with the opamp output.
 5. The TIAcircuit of claim 1 wherein the first voltage is greater than the secondvoltage.
 6. The TIA circuit of claim 1 wherein the third voltage isapproximately equal to a sum of the first voltage and the secondvoltage.
 7. The TIA circuit of claim 1 wherein the first voltage isotherwise applied to analog circuitry and the second voltage isotherwise applied to digital circuitry.
 8. The TIA circuit of claim 1wherein the first voltage is between about 2.5V and 3.3V.
 9. The TIAcircuit of claim 8 wherein the second voltage is about 1.2V.